Frequency converter, orthogonal demodulator and orthogonal modulator

ABSTRACT

A frequency converter comprising a variable gain amplifier which amplifies the local oscillation signal according to a gain control signal and outputs an amplified local signal, an even harmonic mixer which is supplied with an input signal and an amplified local oscillation signal and outputs an output signal whose frequency is a sum of a first frequency of the input signal and a second frequency of two or more even numbered times a frequency of the amplified local oscillation signal, an amplitude detector which is supplied with the amplified local oscillation signal and outputs a direct current signal having an amplitude corresponding to an amplitude of the amplified local oscillation signal, and a comparator which compares the direct current signal of the amplitude detector with the reference direct current signal to generate an output signal as the gain control signal.

CROSS-REFERENCE TO RELATED APPLICATIONS

This application is a division of and claims the benefit of priorityunder 35 USC 120 from U.S. application Ser. No. 10/141,977, filed May10, 2002, now U.S. Pat. No. 6,774,739 and claims the benefit of priorityunder 35 USC §119 from Japanese patent Application No. 2001-141158,filed May 11, 2001, and No. 2002-131266, filed May 7, 2002, the entirecontents of which are incorporated herein by reference.

BACKGROUND OF THE INVENTION

1. Field of the Invention

The present invention relates to a frequency converter, moreparticularly to a frequency converter used for radio communications.

2. Description of the Related Art

A direct conversion receiving system suitable for miniaturization due tothe reduced number of parts has been put to practical use with thepenetration of radio communication terminal such as portable telephone.However, the direct conversion system uses a local oscillation signal(LO signal) of substantially the same frequency as the receiver signal(RF signal) frequency that is received by a radio antenna. For thisreason, the direct conversion system includes a problem such as aself-mixture that the leakage LO signal enters in a receiver signalchannel and becomes a jamming signal. As one method to solve this issuggested a method to use LO signal of approximately half frequency ofthe receiver signal. According to this method, approximately halffrequency of RF signal frequency is used as LO signal frequency.

A direct conversion receiver comprises an even harmonic mixer using halffrequency of RF signal frequency. This direct conversion receiver hasproperty suitable for the direct conversion because this receiver doesnot indicate theoretically sensitivity to the LO signal even if the LOsignal frequency enters in the receiver signal channel. However, theeven harmonic mixer includes a problem that when the LO signal amplitudefluctuates by temperature change, the conversion gain has varied withthis fluctuation, that is, the gain of the receiver does not indicate atarget value.

Further, the gain greatly varies when the LO signal generator which issensitive to the temperature change is used. In order to solve thisproblem, the conventional device has employed a method of inputting theLO signal to a limiting circuit to make the amplitude constant, and theninputting the LO signal to an even harmonic mixer. However, this methodneeds a filter for eliminating the harmonic component because manyharmonic components of the LO signal occur in the limiting circuit.Generally it is difficult to integrate this filter on a chip.

Further, it obstructs an advantage of the direct conversion that thenumber of parts can be reduced to provide the filter between the LOsignal generator and the even harmonic mixer. Since the conversion gainof the even harmonic mixer depends upon fluctuation of the LO signalamplitude, it is difficult to combine the even harmonic mixer with thecheap oscillation circuit by which the LO signal amplitude is fluctuatedin easy.

It is an object of the present invention to provide a frequencyconverter that can utilize an advantage of an even harmonic mixer thatthe sensitivity deterioration due to self-mixture is small, withoutincrease of parts.

BRIEF SUMMARY OF THE INVENTION

According to an aspect of the present invention, there is provided afrequency converter to which an input signal, a local oscillation signaland a reference direct current signal is supplied, the frequencyconverter comprising: a variable gain amplifier which amplifies thelocal oscillation signal according to a gain control signal and outputsan amplified local signal; an even harmonic mixer which is supplied withthe input signal and the amplified local oscillation signal and outputsan output signal whose frequency is a sum of a first frequency of theinput signal and a second frequency of two or more even numbered times afrequency of the amplified local oscillation signal or a differencebetween the first frequency and the second frequency; an amplitudedetector which is supplied with the amplified local oscillation signaland outputs a direct current signal having an amplitude corresponding toan amplitude of the amplified local oscillation signal; and a comparatorwhich compares the direct current signal of the amplitude detector withthe reference direct current signal to generate an output signal as thegain control signal.

According to another aspect of the present invention, there is providedan orthogonal demodulator to which an input signal, a first localoscillation signal, a second local oscillation signal, a first referencesignal, and a second reference signal, the orthogonal demodulatorcomprising: a first frequency converter including: a first variable gainamplifier which amplifies the first local oscillation signal accordingto a first gain control signal, and outputs an amplified first localoscillation signal; a first even harmonic mixer which is supplied withthe input signal and the amplified first local oscillation signal andoutputs an output signal whose frequency corresponds to a differencebetween a frequency of the input signal and a frequency of two or moreeven numbered times a frequency of the amplified first local oscillationsignal; a first amplitude detector which is supplied with the amplifiedfirst local oscillation signal and outputs a first direct current signalhaving an amplitude corresponding to an amplitude of the amplified firstlocal oscillation signal; and a first comparator which compares thefirst reference direct current signal with the first direct currentsignal to generate an output signal as the first gain control signal; asecond frequency converter including: a second variable gain amplifierwhich amplifies the second local oscillation signal according to asecond gain control signal, and outputs an amplified second localoscillation signal; a second even harmonic mixer which is supplied withthe input signal and the amplified second local oscillation signal andoutputs an output signal whose frequency corresponds to a differencebetween a frequency of the input signal and a frequency of two or moreeven numbered times a frequency of the amplified second localoscillation signal; a second amplitude detector which is supplied withthe amplified second local oscillation signal and outputs a seconddirect current signal having an amplitude corresponding to an amplitudeof the amplified second local oscillation signal; and a secondcomparator which compares the second reference direct current signalwith the second direct current signal to generate an output signal asthe second gain control signal; and a phase shifter which outputs thefirst local oscillation signal and the second local oscillation signalwith a given phase difference-therebetween to the first frequencyconverter and the second frequency converter.

BRIEF DESCRIPTION OF THE SEVERAL VIEWS OF THE DRAWING

FIG. 1 is a block diagram of a frequency converter related to the firstembodiment of the present invention;

FIG. 2 shows an example of the even harmonic mixer of FIG. 1;

FIG. 3 shows a circuit configuration of the even harmonic mixer of FIG.2;

FIG. 4 is a block diagram of a frequency converter related to the secondembodiment of the present invention;

FIG. 5 shows a relation between the conversion gain and the amplitude ofLO signal in a case using a pair of differential transistors as the evenharmonic mixer;

FIG. 6 is a block diagram of the second even harmonic mixer;

FIG. 7 is a circuit diagram of a pair of differential field effecttransistors;

FIG. 8 is a block diagram of an orthogonal demodulator related to thethird embodiment of the present invention;

FIG. 9 is a block diagram of a receiver using the orthogonal demodulatorshown in FIG. 8;

FIG. 10 is a block diagram of an orthogonal modulator related to thefourth embodiment of the present invention;

FIG. 11 is a block diagram of a frequency converter related to the fifthembodiment of the present invention;

FIG. 12 is a block diagram of a frequency converter related to the sixthembodiment of the present invention;

FIG. 13 is a block diagram of a frequency converter related to theseventh embodiment of the present invention;

FIG. 14 is a block diagram of a receiver related to the eighthembodiment of the present invention; and

FIG. 15 is a block diagram of a receiver related to the ninth embodimentof the present invention.

DETAILED DESCRIPTION OF THE INVENTION

The embodiments of the present invention will hereinafter be describedwith reference to the attached drawings.

The First Embodiment

FIG. 1 shows a block diagram of frequency converter related to the firstembodiment of the present invention. There will now be described afrequency converter used for a receiving system which down-converts areceived signal (RF signal) received via a radio antenna (not shown).

A frequency converter 100 shown in FIG. 1 comprises an even harmonicmixer 101, a LO signal variable gain amplifier 102, an amplitudedetector 103 and a comparator 104. An input signal (RF signal or amodulated signal) and a local oscillation signal (LO signal) amplifiedby the LO signal variable gain amplifier 102 are input to the evenharmonic mixer 101, so that the input signal is converted to thefrequency corresponding to the difference between the input signal and asignal whose frequency is two or more even numbered times (two times,for example) the LO signal frequency.

The conversion gain of the even harmonic mixer 101 varies according tothe LO signal amplitude. Therefore, the LO signal generated by the localoscillator (not shown) is amplified to a desired LO signal amplitude bythe LO signal variable gain amplifier 102. The LO signal amplified tothe desired amplitude (an output of the LO signal variable gainamplifier 102) is input to the first even harmonic mixer 101. Thedesired LO signal amplitude is the LO signal amplitude by which theconversion gain of the even harmonic mixer becomes maximum when makingmuch account of the noise property of the frequency converter 100. Whenmaking much account of distortion property, it is preferable that thedesired LO signal amplitude is amplified more greatly than the LO signalamplitude that the conversion gain becomes maximum, to obtain the LOsignal amplitude of the status that the conversion gain falls to alittle.

Detection of this amplitude is necessary in order to keep the LO signalamplitude at a desired value. The output of the LO signal variable gainamplifier 102 is input to the amplitude detector 103 and converted intothe direct current signal which met the amplitude. The comparator 104compares the output of the amplitude detector 103 with a referencedirect current signal externally supplied. The output of the comparator104 is input to the LO signal variable gain amplifier 102 as a gaincontrol signal. In other words, the LO signal variable gain amplifier102, amplitude detector 103 and comparator 104 constructs a feedbackloop.

The LO signal amplitude amplified by the LO signal variable gainamplifier 102 is determined by the magnitude of the reference directcurrent signal thanks to this feedback loop. As a result, the conversiongain of the even harmonic mixer 101 is kept uniformity.

Since the frequency converter 100 uses a variable gain amplifier, ithardly generates higher harmonics. For this reason, the filter to removethe higher harmonics is not needed. Thus, the frequency converter 100can be fabricated as an integrated circuit. Although the area of thisintegrated circuit increases somewhat, the number of parts of thereceiver does not increase.

FIG. 2 shows a block diagram of an even harmonic mixer usingdifferential bipolar transistor pairs as one example of the evenharmonic mixer 101 shown in FIG. 1. FIG. 3 shows a concrete circuitconfiguration of the mixer shown in FIG. 2.

This even harmonic mixer 101 uses four sets 201 a to 201 d of thedifferential transistor pairs. The base terminals as input terminals areconnected in bridge. The LO signal and the modulated signal (RF signal)are separated without being directly connected to each other because ofthe bridge-connection. Since a differential transistor pair is used, theLO signal is converted into a differential signal of terminals LO+ andLO− (reverse signal of LO+), and the LO signal and modulated signal areinput to the even harmonic mixer 101 after the RF signal was convertedinto a differential signal of terminals RF+ and RF− (reverse signal ofRF+).

The state that the LO signal leaks to the RF terminal is a cause of theself-mixture. However, in the even harmonic mixer 101 ofbridge-connection, a signal leaked from the LO+ terminal and a signalleaked from the LO− terminal are counteracted to each other as describedbelow. Therefore, no signal leakage is seemingly appeared when viewedfrom the RF+ and RF− terminals. The output terminals of eachdifferential transistor pair are connected so that the LO differentialsignals (LO+, LO−) are counteracted to each other, and desired signalsafter frequency conversion (baseband differential signals BB+ and BB− ofFIG. 3) are emphasized to each other.

A conventional even harmonic mixer is a mixer using an anti-paralleldiodes pair. However, the signal leakage becomes a problem when such amixer is used for the direct conversion. This results from that thediode is a 2-terminal element, and the separation between the input andoutput is only means for separating by frequency. However, in a caseusing transistors, the base terminal is an input, and the collectorterminal is an output. Therefore, the input-to-output separation isassured at least. For this reason, the filter for the signal separationis unnecessary, integration is enabled with a cheap silicon IC. In otherwords, the even harmonic mixer of the frequency converter related to thepresent embodiment can use diodes, but the even harmonic mixer using thedifferential transistor pair is preferable.

The circuit configuration of FIG. 3 will be described hereinafter. FIG.3 shows a circuit configuration of a bridge-connection even harmonicmixer 101 shown in FIG. 2. The differential transistor pair 201 acomprises two npn type bipolar transistors Tr1 a and Tr1 b, and aconstant current source 1 provided between the common emitter terminalof the transistors Tr1 a and Tr1 b and the ground. The base terminal ofthe transistor Tr1 a is connected to the RF+ terminal, and the baseterminal of the transistor Tr1 b is connected to the LO+ terminal. Thecollector terminal of the transistor Tr1 a is connected to a BB+terminal outputting a baseband signal BB+ and the collector terminal ofthe transistor Tr1 b is connected to a BB− terminal outputting abaseband signal BB−.

In the differential transistor pair 201 b, the base terminal of atransistor Tr2 a is connected to the LO+ terminal, and the base terminalof the transistor Tr2 b is connected to the RF− terminal. The collectorterminal of the transistor Tr2 a is connected to the BB+ terminal, andthe collector terminal of the transistor Tr2 b is connected to the BB−terminal.

In the differential transistor pair 201 c, the base terminal of thetransistor Tr3 a is connected to the LO− terminal, and the base terminalof the transistor Tr3 b is connected to the RF− terminal. The collectorterminal of the transistor Tr3 a is connected to the BB+ terminal, andthe collector terminal of the transistor Tr3 b is connected to the BB−terminal.

In the differential transistor pair 201 d, the base terminal of atransistor Tr4 a is connected to the LO+ terminal, and the base terminalof the transistor Tr4 b is connected to the RF− terminal. The collectorterminal of the transistor Tr4 a is connected to the BB+ terminal, andthe collector terminal of the transistor Tr4 b is connected to the BB−terminal. All transistors Tr1 to Tr4 constructing the differentialtransistor pairs are transistors of the same size.

There will be described the reasons that the signal leaked from the LO+terminal and the signal leaked from the LO− terminal are counteracted toeach other in the even harmonic mixer 101 of bridge-connection.

At first, the reason that the signal leaked from the LO+ terminal andthe signal leaked from the LO− terminal are counteracted to each otherin the RF+ terminal will be described. The signal leaked from the LO+terminal to the RF+ terminal is the LO+ signal passing through theemitter and base terminals of the transistor Tr1 a from the base andemitter terminals of the transistor Tr1 b of the differential transistorpair 201 a.

On the other hand, the signal leaked from the LO− terminal to the RF+terminal is the LO− signal passing through the emitter and baseterminals of the transistor Tr4 a from the base and emitter terminals ofthe transistor Tr4 b of the differential transistor pair 201 d. Sincethe transistors constructing the differential transistor pairs 201 a and201 d are of the same size, the leakage routes of the differentialtransistor pairs 201 a and 201 d are of the same impedance. Since theleakage signals are reverse relational, they are counteracted to eachother in the RF+ terminal. Therefore, no leakage signal occurs in anappearance. The similar counteraction occurs in the RF− terminal.Therefore, the signal leaked from the LO+ terminal and the signal leakedfrom the LO− terminal are counteracted to each other in the RF+ and RF−terminals in the even harmonic mixer 101 of bridge-connection.

The Second Embodiment

FIG. 4 shows a circuit configuration of the frequency converter relatedto the second embodiment of the present invention. In the secondembodiment, like reference numerals are used to designate likestructural elements corresponding to those like in the first embodimentand any further explanation is omitted for brevity's sake.

In the frequency converter 200 shown in FIG. 4, the first even harmonicmixer 101 and the second even harmonic mixer 203 are used. Furthermore,the first reference direct current signal is input to the comparator104, and the second reference direct current signal is input to thesecond even harmonic mixer.

FIG. 5 shows a simulation result representing a LO signal amplitudedependency to the conversion gain of the even harmonic mixer modeled bythe differential bipolar transistor pair such as the differentialtransistor pair 201 a of FIG. 2. The abscissa axis shows the amplitudeof the normalized LO signal and the ordinate axis shows the conversiongain. As shown in a solid line, when the input signal (RF signal ormodulated signal) is a signal whose frequency is 2 times LO signalfrequency. The conversion gain (double wave conversion gain) to convertthe input signal to a signal (baseband signal) near the DC increases inaccordance with increase of the LO signal amplitude. This conversiongain reaches a peak by several times the heat voltage Vt (correspondingto 0.5 of the abscissa axis) and decreases thereafter. When the inputsignal has the frequency of 4 times the LO signal frequency, theconversion gain (quadruple wave conversion gain) to convert this inputsignal to the signal near the DC shows a tendency similar to the above.However, the conversion gain (zero wave conversion gain) to output thesignal near the DC at that differs from the conversion gain a little.

When the LO signal is small, the gain becomes maximum. When the LOsignal increases, the gain shows a tendency to be inversely proportionalto the LO signal amplitude. It is a feature of the present embodiment touse the zero wave conversion gain-LO signal amplitude characteristic foramplitude detection of the LO signal. In other words, the presentembodiment uses the feature that the zero wave conversion gain and theLO signal amplitude correspond one-on-one, unlike the double wave orquadruple wave conversion gain.

FIG. 6 shows a circuit configuration of the second even harmonic mixer203 used as the LO signal amplitude detector. The second even harmonicmixer 203 has the same circuit configuration as that of the first evenharmonic mixer 101. However, the second reference direct current signal(DC+, DC−) is input to the second even harmonic mixer 203 in instead ofthe input signal (RF+, RF−). The same parts as those of the first evenharmonic mixer 101 refer to FIGS. 2 and 3 and the details are omitted.

When the second even harmonic mixer 203 fabricated by differentialtransistor pairs is used as an amplitude detector, the LO signalamplitude is in inverse proportion to the output DC signal amplitude ofthe second even harmonic mixer 203. By comparing this output directcurrent signal with the first reference DC signal, the feedback isperformed so that the conversion gain (zero wave conversion gain) fromthe second reference DC signal of the second even harmonic mixer 203 tothe output DC signal becomes a ratio of the first reference DC signal tothe second reference DC signal.

It is possible to make the double wave conversion gain of the first evenharmonic mixer 101 to a desired value by increasing the LO signalamplitude till the zero wave conversion gain of the second even harmonicmixer 203 as an amplitude detector becomes a desired value. This can beconsidered to be a master slave controller which uses the second evenharmonic mixer 203 as a master circuit and the first even harmonic mixer101 as a slave circuit. If the second even harmonic mixer 203 is used asan amplitude detector in the feedback loop, it is possible not only tomake the conversion gain constant regardless of variation of the LOsignal amplitude, but also to suppress variation of the gain due to thecharacteristic variation of the transistor that causes by thetemperature variation.

When the characteristic of the transistor varies by a temperaturechange, the first even harmonic mixer 101 and the second even harmonicmixer 203 as an amplitude detector receive the same affect. Therefore,the LO signal amplitude is adjusted by the feedback loop so that thegain of the second even harmonic mixer 203 become a desired gain. As aresult, the gain of the first even harmonic mixer 101 is compensated,too.

FIG. 7 shows a circuit diagram of a differential transistor pair 301using field effect transistors (FET). Even if FETs such as MOStransistors are used, it is possible to fabricate the first and thesecond even harmonic mixers 101 and 203 similarly to the differentialtransistor pairs 201 a to 201 d using the bipolar transistors. However,it is difficult to obtain the conversion gain according to the designsince the threshold of the FET and so on fluctuates dependant upon amanufacturing process of a semiconductor device. However, the specialfeature of the integrated circuit that the characteristics oftransistors on the same chip are approximately the same is common to thebipolar transistor and the FET. The frequency converter of the presentembodiment uses the second even harmonic mixer 203 as an amplitudedetector as a master circuit, determines the LO signal amplitudereferring to the conversion gain, and controls the conversion gain ofthe first even harmonic mixer 101 as the slave circuit. For this reason,if the FET having large characteristic variation in comparison with thebipolar transistor is used, the conversion gain can be kept at a desiredvalue.

The above-mentioned explanation is based on the frequency converter usedfor the receiver system, but the present embodiment can be applied to atransmitter system. In this case, the input signal input to thefrequency converter 100 is a modulating signal generated by convertinginformation of a speech signal to a digital signal. This modulatingsignal is converted to a signal whose frequency is the sum of afrequency of two or more even numbered times (two times, for example)the LO signal frequency and the frequency of the modulating signal. Theconverted signal is output as the RF signal. This RF signal istransmitted via a radio antenna (not shown).

The Third Embodiment

FIG. 8 shows a configuration of an orthogonal demodulator according tothe third embodiment of the present invention. The orthogonaldemodulator 400 shown in FIG. 8 comprises two frequency converters 401and 402 related to the first and second embodiments and a phase shifter403. Assumed that the frequency converter 401 and 402 mix a RF signalwave and a double wave of the LO signal. An inphase signal (RF signal ormodulated signal) is input to two frequency converters 401 and 402. Thephase shifter 403 outputs LO signals having a phase difference of 45° tothe two frequency converters 401 and 402.

The frequency converters 401 and 402 convert the RF input signal to asignal whose frequency is lowered by the frequency of 2 times the LOsignal frequency, and divide it into an I channel signal (I signal) anda Q channel signal (Q signal) of baseband. The frequency converters 401and 402 mix the double wave of the LO signal with the RF signal wave, sothat the phase difference of 45° is changed to the phase difference of90°. For this reason, the phase difference of the phase shifter 403 isset to 45°. Therefore, the phase difference of the phase shifter 403 maybe set to 22.5° when the frequency converters 401 and 402 mix thequadruple wave of the LO signal with the RF signal wave.

In the orthogonal demodulator 400 related to the present embodiment, avariable gain amplifier is used for the frequency converters 401 and402. Therefore, there is not a problem that the higher harmonics of theLO signal occurs. Thus, the orthogonal demodulator 400 can beconstructed as an integrated circuit. The I signal and Q signal ofprecision equal to that of a conventional orthogonal demodulator can beobtained without increase of the number of parts only by inputting theoutput of the phase shifter 403 to the frequency converters 401 and 402.

FIG. 9 shows a configuration of a receiver using the orthogonaldemodulator 400 shown in FIG. 8. The receiver comprises a radio antenna(ANT) 501 to receive a RF signal, a low noise amplifier (LNA) 502 toamplify the RF signal, a band pass filter (BPF) 503 to filter an outputof the low-noise amplifier, and an orthogonal demodulator 400 toorthogonal-demodulate the output of the band pass filter 503, and outputan I-signal and a Q-signal.

A LO signal generator 504 to generate a local oscillation signal (LOsignal) input to an orthogonal demodulator, and low pass filters (LPF)505 a and 505 b which receive the I signal and Q-signal and extract andoutput the low frequency components are provided. Amplifiers (AMP) 506 aand 506 b which amplify the outputs of low pass filters 505 a and 505 band a demodulator 507 which demodulates data such as speech based on theoutputs of the amplifiers 506 a and 506 b are provided.

In the receiver shown in FIG. 9, the orthogonal demodulator 400 can beconstructed as one integrated circuit as described heretofore. Also, alow-noise amplifier 502, a low pass filter 503, an orthogonaldemodulator 400, low pass filters 505 a and 505 b, and amplifiers 506 aand 506 b can be constructed as one integrated circuit.

The Fourth Embodiment

FIG. 10 shows a configuration of an orthogonal modulator related to thefourth embodiment of the present invention. The embodiment of FIG. 10 isan orthogonal modulator 600 applied to the transmitter. The orthogonalmodulator 600 has the same circuit configuration as that of theorthogonal modulator 400 shown in FIG. 8. However, the input-outputdirection differs from the orthogonal modulator 400 of FIG. 8. In otherwords, the input signals of the orthogonal modulator 600 are I-signaland Q-signal of baseband. The output of the frequency converter 401 andthe output of the frequency converter 402 are added to generate anoutput signal. This output signal is a RF signal.

FIG. 11 shows a configuration of the frequency converter related to thefifth embodiment of the present invention. The configuration of thefrequency converter of the present embodiment is the same as that of thefrequency converter shown in FIG. 1, but the reference DC signal inputto the comparator 104 is variable. The conversion gain of the evenharmonic mixer 101 varies according to the LO signal amplitude asdescribed above. Therefore, when the conversion gain is changed in thefrequency converter in order to obtain the dynamic range of thereceiver, for example, the LO signal amplitude may be varied accordingto a desired conversion gain. For this reason, the reference DC signalcompared with the output DC signal of the amplitude detector 103 in thecomparator 104 is changed. The gain of the variable gain amplifier 102is changed according to a result of comparison of this variablereference DC signal with the output signal of the amplitude detector103. In other words, changing the reference DC signal voluntarilyprovides a desired dynamic range of the receiver.

FIG. 12 shows a configuration of a frequency converter related to thesixth embodiment of the present invention. The configuration of thefrequency converter of this embodiment is substantially the same as thatof frequency converter shown in FIG. 4, but the second reference DCsignal input to the second even harmonic mixer 203 is variable. Changingthe second reference DC signal voluntarily can vary the output signal ofthe second even harmonic mixer 203. This output signal is input to thecomparator 104 and is compared with the reference DC signal. The gain ofthe variable gain amplifier 102 can be changed according to a comparisonresult of the comparator 104. In other words, the gain of the variablegain amplifier 102 is changed according to a change of the secondreference DC signal.

As thus described, the frequency converter of the present embodiment canbe used as a frequency converter having a variable gain function. Thefirst reference DC signal may be variable in this embodiment, too.

FIG. 13 shows a configuration of a frequency converter related to theseventh embodiment of the present invention. The configuration of thefrequency converter of this embodiment is substantially the same as thatof the frequency converter shown in FIG. 4, but in this embodiment, eachof the first and second even harmonic mixers 101 and 203 comprises adifferential transistor pair Tr and a variable current source I. In thisembodiment, distortion property and noise property can be kept inpreferable status with a constant conversion gain by changing a tailcurrent according to an input signal level. As a result, a current canbe increased only when making the frequency converter activate withpreferable status of the distortion property, but the current can bedecreased when making it to activate with other status. This makes adesired dynamic range ensure with a low consumption current.

FIG. 14 shows a configuration of a receiver using an orthogonaldemodulator related to the eighth embodiment of the present invention.The present embodiment corresponds to the embodiment of FIG. 9, but inthe present embodiment, received signal status detectors 508 a and 508 bare connected to LPFs 505 a and 505 b. The received signal statusdetectors 508 a and 508 b detects a power of the whole signal input tothe LPFs and a level of a desired wave or an interference wave using atleast one of an input of the LPFs and an intermediate output of theLPFs. The detected signals of the received signal status detectors 508 aand 508 b are input to the controllers 509 a and 509 b. The controllers509 a and 509 b set the frequency converters 401 and 402, respectively,to such bias states that the frequency converter operates with the statethat the distortion property of the frequency converter is preferablewhen the interference wave level is large.

As thus described, the receiver of high-performance and low powerconsumption can be realized by operating the frequency converters 401and 402 with reasonable bias condition according to the received signalstatus.

FIG. 15 shows a configuration of a receiver using an orthogonaldemodulator related to the eighth embodiment of the present invention.This embodiment corresponds to the embodiment of FIG. 9, too, but RSSI(Received Signal Strength Indicator) detectors 510 a and 510 areprovided as received signal status detectors in the present embodiment.Further variable gain amplifiers (VGA) 511 a and 511 b are provided onthe rear stages of the LPFs 505 a and 505 b, respectively.

The controllers 512 a and 512 b set the conversion gains of thefrequency converters 401 and 402 so as to provide desired receptioncharacteristics according to the reception electrolysis strengthdetected by the RSSI detectors 510 a and 510 b, and set gains of VGAs512 a and 512 b so that the gain of the whole receiver becomes constant.For example, when the reception electrolysis strength is strong, theconversion gains of the frequency converters 401 and 402 are decreased,and the gains of the VGA 512 a and 512 b are increased. On the otherhand, when the reception electrolysis strength is weak, the conversiongains of the frequency converters 401 and 402 are increased and thegains of the VGA 512 a and 512 b are decreased. As a result, the gaindistribution of the frequency converter 401 and 402 and the VGA 512 aand 512 b can be optimized.

In the above embodiments, the conductivity type of the transistors Tr1to Tr4 of FIG. 3 may be pnp type. Further, the first channel type of FETof FIG. 7 may be p channel type, if all FETs constructing the first andsecond even harmonic mixers 101 and 203 are the same channel type.

Additional advantages and modifications will readily occur to thoseskilled in the art. Therefore, the invention in its broader aspects isnot limited to the specific details and representative embodiments shownand described herein. Accordingly, various modifications may be madewithout departing from the spirit or scope of the general inventiveconcept as defined by the appended claims and their equivalents.

1. A receiver comprising: an orthogonal demodulator using an inputsignal, a first local oscillation signal, a second local oscillationsignal, a first reference signal, and a second reference signal, theorthogonal demodulator comprising a first frequency converter, a secondfrequency converter, and a phase shifter; the first frequency converterincluding: a first variable gain amplifier which amplifies the firstlocal oscillation signal according to a first gain control signal, andoutputs an amplified first local oscillation signal; a first evenharmonic mixer which is supplied with the input signal and the amplifiedfirst local oscillation signal and outputs an output signal whosefrequency corresponds to a difference between a frequency of the inputsignal and a frequency of two or more even numbered times a frequency ofthe amplified first local oscillation signal; a first amplitude detectorwhich is supplied with the amplified first local oscillation signal andoutputs a first direct current signal having an amplitude correspondingto an amplitude of the amplified first local oscillation signal; and afirst comparator which compares the first reference signal with thefirst direct current signal to generate an output signal as the firstgain control signal; the second frequency converter including: a secondvariable gain amplifier which amplifies the second local oscillationsignal according to a second gain control signal, and outputs anamplified second local oscillation signal; a second even harmonic mixerwhich is supplied with the input signal and the amplified second localoscillation signal and outputs an output signal whose frequencycorresponds to a difference between a frequency of the input signal anda frequency of two or more even numbered times a frequency of theamplified second local oscillation signal; a second amplitude detectorwhich is supplied with the amplified second local oscillation signal andoutputs a second direct current signal having an amplitude correspondingto an amplitude of the amplified second local oscillation signal; and asecond comparator which compares the second reference signal with thesecond direct current signal to generate an output signal as the secondgain control signal; and the phase shifter outputting the first localoscillation signal and the second local oscillation signal with a givenphase difference therebetween to the first frequency converter and thesecond frequency converter; a received signal state detector configuredto detect a received signal state and output a detection signal; and acontroller supplied with the detection signal and configured to output acontrol signal used for setting a conversion gain and an operation stateto the first frequency converter and the second frequency converter. 2.The receiver according to claim 1, wherein the phase difference is 90when the frequency of the input signal is n times the frequency of thefirst local oscillation signal and the second local oscillation signal,where n is two or more even number.
 3. The receiver according to claim1, which further comprises first and second low pass filters and whereinthe received signal state detector comprises first and second receivedsignal state detector units configured to detect powers of signals inputto the first and second low pass filters, respectively, and thecontroller comprises first and second controller units configured tocontrol the first frequency converter and the second frequency converteron bias states, respectively, according to detected results of the firstand second received signal state detector units.
 4. A transmittercomprising: an orthogonal modulator using an input signal, a first localoscillation signal, a second local oscillation signal, a first referencesignal, and a second reference signal, the orthogonal demodulatorcomprising a first frequency converter, a second frequency converter,and a phase shifter: the first frequency converter including: a firstvariable gain amplifier which amplifies the first local oscillationsignal according to a first gain control signal, and outputs anamplified first local oscillation signal; a first even harmonic mixerwhich is supplied with an I signal of baseband and the amplified firstlocal oscillation signal and outputs an output signal whose frequencycorresponds to a sum of a frequency of the input signal and a frequencyof two or more even numbered times a frequency of the amplified firstlocal oscillation signal; a first amplitude detector which is suppliedwith the amplified first local oscillation signal and outputs a firstdirect current signal having an amplitude corresponding to an amplitudeof the amplified first local oscillation signal; and a first comparatorwhich compares the first reference signal with the first direct currentsignal to generate an output signal as the first gain control signal;the second frequency converter including: a second variable gainamplifier which amplifies the second local oscillation signal accordingto a second gain control signal, and outputs an amplified second localoscillation signal; a second even harmonic mixer which is supplied witha Q signal of baseband and the amplified second local oscillation signaland outputs an output signal whose frequency corresponds to a sum of afrequency of the Q signal and a frequency of two or more even numberedtimes a frequency of the amplified second local oscillation signal; asecond amplitude detector which is supplied with the amplified secondlocal oscillation signal and outputs a second direct current signalhaving an amplitude corresponding to an amplitude of the amplified firstlocal oscillation signal; and a second comparator which compares thesecond reference signal with the second direct current signal togenerate an output signal as the second gain control signal; and thephase shifter outputting the first local oscillation signal and thesecond local oscillation signal with a given phase differencetherebetween to the first frequency converter and the second frequencyconverter; a signal state detector configured to detect states of the Isignal and the Q signal and output a detection signal; and a controllersupplied with the detection signal and configured to output a controlsignal used for setting a conversion gain and an operation state to thefirst frequency converter and the second frequency converter.
 5. Atransmitter according to claim 4, wherein the phase difference is 90when the frequency of the I signal and the Q signal are n times thefrequency of the first local oscillation signal and the second localoscillation signal, where n is two or more even number.
 6. Thetransmitter according to claim 4, which further comprises first andsecond low pass filters and wherein the signal state detector comprisesan I signal state detector unit and a Q signal state detector unitconfigured to detect powers of signals input to the first and second lowpass filters, respectively, and the controller comprises first andsecond controller units configured to control the first frequencyconverter and the second frequency converter on bias states,respectively, according to detected results of the I signal statedetector unit and the Q signal state detector unit.